Volume 41 – May 2007
Ask The Applications Engineer—37
By Jerome Patoux [firstname.lastname@example.org]
This article introduces the basic topologies and suggests good practical usage for ensuring stable operation of low-dropout voltage regulators (LDOs). We will also discuss design characteristics of Analog Devices families of LDOs, which offer a flexible approach to maintaining dynamic- and dc stability.
Q: What are LDOs and how are they used?
A: Voltage regulators are used to provide a stable power supply voltage independent of load impedance, input-voltage variations, temperature, and time. Low-dropout regulators are distinguished by their ability to maintain regulation with small differences between supply voltage and load voltage. For example, as a lithium-ion battery drops from 4.2 V (fully charged) to 2.7 V (almost discharged), an LDO can maintain a constant 2.5 V at the load.
The increasing number of portable applications has thus led designers to consider LDOs to maintain the required system voltage independently of the state of battery charge. But portable systems are not the only kind of application that might benefit from LDOs. Any equipment that needs constant and stable voltage, while minimizing the upstream supply (or working with wide fluctuations in upstream supply), is a candidate for LDOs. Typical examples include circuitry with digital and RF loads.
A “linear” series voltage regulator (Figure 1) typically consists of a reference voltage, a means of scaling the output voltage and comparing it to the reference, a feedback amplifier, and a series pass transistor (bipolar or FET), whose voltage drop is controlled by the amplifier to maintain the output at the required value. If, for example, the load current decreases, causing the output to rise incrementally, the error voltage will increase, the amplifier output will rise, the voltage across the pass transistor will increase, and the output will return to its original value.
Figure 1. Basic enhancement-mode PMOS LDO.
In Figure 1, the error amplifier and PMOS transistor form a voltage-controlled current source. The output voltage, VOUT, is scaled down by the voltage divider (R1, R2) and compared to the reference voltage (VREF). The error amplifier's output controls an enhancement-mode PMOS transistor.
The dropout voltage is the difference between the output voltage and the input voltage at which the circuit quits regulation with further reductions in input voltage. It is usually considered to be reached when the output voltage has dropped to 100 mV below the nominal value. This key factor, which characterizes the regulator, depends on load current and junction temperature of the pass transistor.
Q: How are regulators distinguished by dropout voltage?
A: We can suggest three classes: standard regulators, quasi-LDOs, and low-dropout regulators (LDOs).
Standard regulators, which typically employ NPN pass transistors, usually drop out at about 2 V.
Quasi-LDO regulators usually use a Darlington structure (Figure 2) to implement a pass device made up of an NPN transistor and a PNP. The dropout voltage, VSAT (PNP) + VBE (NPN), is typically about 1 V—more than an LDO but less than a standard regulator.
Figure 2. Quasi-LDO circuit.
LDO regulators are usually the optimal choice based on dropout voltage, typically 100 mV to 200 mV. The disadvantage, however, is that the ground-pin current of a LDO is usually higher than that of a quasi-LDO or a standard regulator.
Standard regulators have a higher dropout voltage and dissipation, and lower efficiency, than the other types. They can be replaced by LDO regulators much of the time, but the maximum input voltage specification—which can be lower than that for standard regulators—should be considered. In addition, some LDOs will need specially chosen external capacitors to maintain stability. The three types differ somewhat in both bandwidth and dynamic stability considerations.
Q: How can I select the best regulator for my application?
A: To choose the right regulator for a specific application, the type and range of input voltage (e.g., the output voltage of the dc-to-dc converter or switching power supply ahead of the regulator), needs to be considered. Also important are: the required output voltage, maximum load current, minimum dropout voltage, quiescent current, and power dissipation. Often, additional features may be useful, such as a shutdown pin or an error flag to indicate loss of regulation.
The source of the input voltage needs to be considered in order to choose a suitable category of LDO. In battery-powered applications, LDOs must maintain the required system voltage as the battery discharges. If the dc input voltage is provided from a rectified ac source, the dropout voltage may not be critical, so a standard regulator—which may be cheaper and can provide more load current—could be a better choice. But an LDO could be the right choice if lower power dissipation or a more precise output voltage is necessary.
The regulator should, of course, be able to provide enough current to the load with specified accuracy under worst-case conditions.
Examples of four types of pass devices are shown in Figure 3, including NPN and PNP bipolar transistors, Darlington circuits, and PMOS transistors.
Figure 3. Examples of pass devices.
For a given supply voltage, the bipolar pass devices can deliver the highest output current. A PNP is preferred to an NPN, because the base of the PNP can be pulled to ground, fully saturating the transistor if necessary. The base of the NPN can only be pulled as high as the supply voltage, limiting the minimum voltage drop to one VBE. Therefore, NPN and Darlington pass devices can’t provide dropout voltages below 1 V. They can be valuable, however, where wide bandwidth and immunity to capacitive loading are necessary (thanks to their characteristically low ZOUT).
PMOS and PNP transistors can be effectively saturated, minimizing the voltage loss and the power dissipated by the pass device, thus allowing low dropout, high-efficiency voltage regulators. PMOS pass devices can provide the lowest possible dropout voltage drop, approximately RDS(ON) × IL. They also allow the quiescent current flow to be minimized. The main drawback is that the MOS transistor is often an external component—especially for controlling high currents—thus making the IC a controller, rather than a complete self-contained regulator.
The power loss in a complete regulator is
PD = (VIN – VOUT ) IL + VIN IGND
The first part of this relationship is the dissipation of the pass device; the second part is the power consumption of the controller portion of the circuit. The ground current in some regulators, especially those using saturable bipolar transistors as pass devices, can peak during power-up.
Q: How can LDO dynamic stability be ensured?
A: Classical LDO circuit designs for general-purpose applications have problems with stability. The difficulties stem from the nature of their feedback circuits, the wide range of possible loads, the variability of elements within the loop, and the difficulty of obtaining precision compensation devices with consistent parameters. These considerations will be discussed below, followed by a description of the anyCAP® circuit topology, which has improved stability.
LDOs generally use a feedback loop to provide a constant voltage, independent of load, at the output. As is true for any high-gain feedback loop, the location of the poles and zeros in the loop-gain transfer function will determine the stability.
NPN-based regulators, with their low-impedance emitter-loaded output, tend to be relatively insensitive to output capacitive loading. PNP and PMOS regulators, however, have higher output impedance (collector loaded in the case of the PNP). In addition, the loop’s gain and phase characteristics strongly depend on the load impedance, thus requiring special consideration for stability.
The transfer function of PNP- and PMOS-based LDOs has several poles that impact stability:
Figure 4. LDO frequency amplitude response.
As Figure 4 shows, each pole contributes 20 dB/decade of roll-off in gain, with up to 90° of phase shift. As the LDOs discussed here have multiple poles, the linear regulator will be unstable if the phase shift at the unity-gain frequency approaches –180°. Figure 4 also shows the effect of loading the regulator with a capacitor, whose effective series resistance (ESR) will add a zero (ZESR) into the transfer function. This zero will help to compensate for one of the poles and can help to stabilize the loop if it occurs below the unity-gain frequency and keeps the phase shift well below –180° at that frequency.
ESR can be critical for stability, especially for LDOs with vertical-PNP pass devices. As a parasitic property of a capacitor, however, the ESR is not always well-controlled. A circuit may require the ESR to fall within a certain window to ensure that the LDO operates in the stable region for all output currents (Figure 5).
Figure 5. Stability as a function of output current and load-capacitor ESR.
Even in principle, choosing the right capacitor with the right ESR (high enough to reduce the slope before the frequency response crosses through 0 dB, yet low enough to bring the gain below 0 dB before the associated pole, P2) can be challenging. Yet the practical considerations add further challenges: ESR varies, depending on the brand; and the minimum capacitance value to use in production will require bench tests, including extreme cases with minimum ambient temperature and maximum load. The choice of the type of capacitor is also important. Perhaps the most suitable are tantalum capacitors, despite their large size in the higher-capacitance ranges. Aluminum electrolytics are compact, but their ESR tends to deteriorate at low temperatures, and they don't work well below –30°C. Multilayer ceramic types do not have sufficient capacitance for conventional LDOs (but they are suitable for anyCAP designs, read on).
Devices anyCAP family of LDOs
Figure 6. Simplified schematic of anyCAP LDO.
The anyCAP family of LDOs, including the 100-mA ADP3307 and the 200-mA low-quiescent-current ADP3331, can remain stable with output capacitance as low as 0.47 µF, using good-quality capacitors of any type, including compact multilayer ceramic. ESR is essentially a nonissue.
The simplified schematic of Figure 6 shows how a single loop provides both regulation and reference functions. The output is sensed by the external R1-R2 voltage divider, and fed back to the input of a high-gain amplifier through diode D1 and the R3-R4 divider. At equilibrium, the amplifier produces a large, repeatable, well-controlled offset voltage that is proportional to absolute temperature (PTAT). This voltage combines with the complementary temperature-sensitive diode voltage drop to form the implicit reference, a temperature-independent virtual band-gap voltage.
The amplifier output connects to an unusual noninverting driver that controls the pass transistor, allowing the frequency compensation to include the load capacitor in a pole-splitting arrangement based on Miller compensation. This provides reduced sensitivity to value, type, and ESR of the load capacitor. Additional advantages of the pole-splitting scheme include superior line-noise rejection and very high regulator gain, thereby providing exceptional accuracy and excellent line and load regulation.
Q: Would you discuss the Analog Devices families of LDOs?
A: The choice of LDO depends, of course, on the supply voltage range, load voltage, and required maximum dropout voltage. The main differences between devices focus on power consumption, efficiency, price, ease of use, and the various specifications and packages available.
The popular ADP33xx anyCAP family of ADI LDOs has been on the market for several years. Based on a BiCMOS process and a PNP pass transistor, it allows good regulation and many of the advantages mentioned above, but tends to be somewhat more expensive than CMOS parts.
Some recent designs, such as the ADP17xx family, are entirely CMOS-based, with a PMOS pass transistor, which allows the fabrication of LDOs at lower cost, but with a trade-off on line-regulation performance. Devices in this family can handle a large range of output capacitance, but they still require at least 1 µF and ≤500-mohm ESR. For example, the 150-mA ADP1710 and ADP1711 are optimized for stable operation with small 1-µF ceramic output capacitors, allowing for good transient performance while occupying minimal board space, and the 300-mA ADP1712, ADP1713, and ADP1714 can use ≥2.2-µF capacitors.
Both of these families have 16 fixed-output-voltage options, from 0.75 V to 3.3 V, as well as an adjustable-output option in the 0.8-V to 5-V range. Accuracy is to within ±2% over line, load, and temperature. The ADP1711 and ADP1713 fixed-voltage versions allow for a reference-bypass capacitor to be connected; this reduces output voltage noise and improves power-supply rejection. The ADP1714 includes a tracking feature, which allows the output to follow an external voltage rail or reference. Dropout voltages at rated load are 150 mV for the ADP1710 and ADP1711; and 170 mV for the ADP1712, ADP1713, and ADP1714. Power-supply rejection (PSR) is high (69 dB and 72 dB at 1 kHz), and power consumption is low, with ground current of 40 µA and 75 µA with 100-µA load.
Typical transient responses of the ADP1710 and ADP1711 are compared in Figure 7 for a nearly full-load step, with 1-µF and 22-µF input- and output capacitors.
Figure 7. Transient response of ADP1710/ADP1711.
The operating junction temperature range is –40°C to +125°C. Both families are available in tiny 5-lead TSOT packages, a small-footprint solution to the variety of power needs.
Copyright 1995- Analog Devices, Inc. All rights reserved.