Volume 36, Number 1, January-February, 2002
Download this article in PDF format. (98 KB)
X-Amp, A New 45-dB, 500-MHz Variable-Gain Amplifier (VGA) Simplifies Adaptive Receiver Designs
Receivers can be designed to provide adaptive sensitivity to incoming signal strength by employing variable gain at the lower IF frequencies, where it is easier to manipulate the signal of interest. Most spectral grooming (frequency shaping and filtering) tends to be implemented at the lower IF frequencies where very narrow-band pass filters can be easily realized through the use of SAW devices, crystals, and passive lumped-element RLC filter networks. After precise channel selection, automatic gain-control (AGC) circuitry can be employed to scale the received signal to a desired level. The use of AGC yields a receiver design whose sensitivity varies, based on received signal strength. Adaptive sensitivity reduces the effects of distance inherent in fading-channel mobile environments. High-performance variable-gain amplifiers are often necessary to provide the needed dynamic range and noise performance.
Figure 1. Typical variable-gain architectures.
A variety of architectures are commonly used to provide both continuous and discrete variable gain control. Applications such as automatic gain control often require continuous analog gain control. The most straightforward designs utilize analog multipliers followed by fixed-gain buffer amplifiers. Such designs often involve a nonlinear gain control function that requires calibration. Additionally, the multiplier cores suffer from temperature and supply-voltage dependencies that can result in poor gain-law accuracy and stability, as well as unacceptable high-frequency gain variation. Designs that use pre-amplifier/attenuator/post-amplifier architectures can provide low-noise operation and good bandwidth, but tend to have quite low input third-order intercept (IIP3), limiting their ability to perform in high-dynamic-range receivers.
Another class of solutions utilizes voltage-variable attenuators, followed by fixed-gain post-amplification. VVAs can provide an accurate attenuation transfer function that is linear in dB, but it is often necessary to cascade multiple VVAs in order to provide adequate attenuation range. The cascading results in an increased sensitivity to variations of the attenuation transfer function. It is sometimes necessary to preamplify the signal to buffer the signal source from the loading effects of the VVA, as well as to decrease the attenuator’s influence on noise figure. The high gain required to yield a low noise figure results in a decreased input third-order intercept.
Figure 2. Architecture of the AD8367 X-Amp VGA.
The AD8367 X-AMP VGA with AGC
As Figure 2 shows, the input signal is applied to a ground-referenced 9-stage R-nR resistive ladder network, designed to produce 5-dB steps of attenuation between tap points. Smooth gain control is achieved by sensing the tap points with variable-transconductance (gm) stages. Depending on the gain-control voltage, an interpolator selects which stages are active. For example, if the first stage is active, the 0-dB tap point is sensed; if the last stage is active, the 45-dB point is sensed. Attenuation levels that fall between tap points are achieved by having neighboring gm stages active simultaneously, creating a weighted average of the discrete tap-point attenuations. In this manner, a smooth, monotonic, linear-in-dB attenuation function with very precise scaling is synthesized. The ideal linear-in-dB transfer function can be expressed as:
MY is the gain scale (slope) usually expressed in dB/V, typically 50 dB/V (or 20 mV/dB)
BZ is the gain intercept in dB, typically –5 dB, the extrapolated gain for VGAIN = 0 V.
VGAIN is the gain-control voltage
The AD8367’s basic connection outline, gain transfer function, and typical gain-error pattern are illustrated in Figure 3, showing the gain transfer function’s slope of 50 dB/V and –5-dB intercept over a gain-control voltage range of 50 mV £ VGAIN £ 950mV. The device allows the gain slope to be reversed by a simple pin-strap of the MODE pin. The inverse gain mode is convenient in automatic gain control (AGC) applications, where the gain control function is derived from an error integrator, which compares the detected output power to a pre-determined set-point level. A square-law detector and the error integrator, integrated on-chip, allow the device to be used as a self-contained AGC subsystem.
A typical stand-alone AGC circuit is shown in Figure 4, along with its time-domain response to a 10-dB input voltage step. In this example the signal input is a 70-MHz sinusoid, and its input is step modulated from –17 to –7 dBm (referred to 200 ohms). The output signal power is measured as a voltage by the internal square-law detector and compared to an internal 354-mV rms reference. The output of the detector is a current, which is integrated using an external capacitor, CAGC. The voltage that is developed across the CAGC capacitor drives the GAIN pin to reduce or increase the gain. The loop is stabilized when the output signal level’s rms value becomes equal to the internal 354-mV reference. When the input signal is less than 354-mV rms, the DETO pin sinks current which reduces the voltage at the GAIN pin. As the input signal increases above 354 mV rms, the DETO pin sources current causing the voltage at the GAIN pin to increase. The inverse gain mode is required in this application to ensure that the gain decreases when the input signal’s rms value exceeds the internal reference. The resulting voltage applied to the GAIN pin, VAGC, can be used as a received-signal-strength indication (RSSI), representing the input signal strength as compared to a 354-mV rms reference. For a sinusoidal waveform this results in a 1-V p-p output signal for a 200-ohm load.
Figure 4. Basic AD8367 AGC application circuit and time-domain response at 70 MHz.
Signal Chain Analysis
Considering the receive path, the overall sensitivity and dynamic range can be assessed using signal-path budget analysis. For this example a PCS-CDMA signal was selected, using a 1-MHz noise bandwidth. Working backwards from the output of the AD8367 IF VGA, the input sensitivity and dynamic range can be analyzed. Figure 6 represents a detailed budget analysis from the receiver input to the output of the IF VGA.
Figure 6. Rx Path Budget Analysis for 1900-MHz CDMA with a 70-MHz IF.
In the example above, the AD8367 controls received signal levels prior to the I&Q demodulator. The AD8367 is an example of a VGA that uses variable attenuation followed by a post-gain amplifier. This style of VGA will exhibit essentially a constant OIP3 and a noise figure that varies with gain setting. The AD8367 provides minimum noise figure at maximum gain and maximum input third-order intercept at minimum gain. This unique combination allows for dynamic control of a receiver’s sensitivity and input linearity, based upon received signal strength.AD8367 (click on this link for data sheets and further information) is characterized over temperature from –40 to +85° C and is packaged in a 14-lead thin-shrunk small-outline package (TSSOP). It operates on a single 3- to 5-volt supply. The device has a –3-dB operating bandwidth of 500 MHz; and its data sheet provides detailed specifications at common IF frequencies—such as 70 MHz, 140 MHz, 190 MHz and 240 MHz. If you are reading the PDF or printed version of this article, please visit www.analog.com to download the data sheet or to request samples. The AD8367 is normally available from stock, and an evaluation board is also available.