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Features & Benefits
 High IF Sampling Receiver
 127MHz Bandpass filter
 SNR = 71.7dBFS, SFDR = 92dBc
Circuit Function & Benefits
The circuit, shown in Figure 1, is a narrow, bandpass receiver front end based on the ADL5565 ultralow noise differential amplifier driver and the AD9642 14bit, 250 MSPS analogtodigital converter (ADC).
The thirdorder, Butterworth antialiasing filter is optimized based on the performance and interface requirements of the amplifier and ADC. The total insertion loss due to the filter network and other components is only 5.8 dB.
The overall circuit has a bandwidth of 18 MHz with a passband flatness of 3 dB. The signaltonoise ratio (SNR) and spuriousfree dynamic range (SFDR) measured with a 127 MHz analog input are 71.7 dBFS and 92 dBc, respectively. The sampling frequency is 205 MSPS, thereby positioning the IF input signal in the second Nyquist zone between 102.5 MHz and 205 MHz.
Circuit Description
An input signal of 1.5 dBm produces a fullscale 1.75 V pp differential signal at the ADC input.
The antialiasing filter is a thirdorder, Butterworth filter designed with a standard filter design program. A Butterworth filter was chosen because of its passband flatness. A thirdorder filter yields an ac noise bandwidth ratio of 1.05 and can be designed with the aid of several free filter programs such as Nuhertz Technologies Filter Free, or the quite universal circuit simulator (Qucs) free simulation.
To achieve best performance, load the ADL5565 with a net differential load of 200 Ω. The 15 Ω series resistors isolate the filter capacitance from the amplifier output, and the 100 Ω resistors in parallel with the downstream impedance yield a net load impedance of 217 Ω when added to the 30 Ω series resistance.
The 5 Ω resistors in series with the ADC inputs isolate internal switching transients from the filter and the amplifier.
The 2.85 kΩ input impedance was determined using the downloadable spreadsheet on the AD9642 webpage. Simply use the parallel track mode values at the center of the IF frequency of interest. The spreadsheet shows both the real and imaginary values.
The internal 2.5 pF capacitance of the ADC was subtracted from the value of the second shunt capacitor to yield a value of 37.3 pF. In the circuit, this capacitor was located near the ADC to reduce/absorb the charge kickback.
The values chosen for the final filter passive components (after adjusting for actual circuit parasitics) are shown in Figure 1.The measured performance of the system is summarized in Table 1, where the 3 dB bandwidth, 18 MHz centered at 127 MHz. The total insertion loss of the network is approximately 5.8 dB. The frequency response is shown in Figure 3, and the SNR and SFDR performance are shown in Figure 4.
Table 1. Measured Performance of the Circuit
Performance Specifications at 1 dBFS (FS = 1.75 V pp), Sample Rate = 205 MSPS  Final Results 
Center Frequency  127 MHz 
PassBand Flatness (118 MHz to 136 MHz)  3 dB 
SNRFS at 127 MHz  71.7 dBFS 
SFDR at 127 MHz  92 dBc 
H2/H3 at 127 MHz  93 dBc/92 dBc 
OverallGain at 127 MHz  5.5 dB 
Input Drive at 127 MHz  0.5 dBm (1 dBFS) 
Figure 3. PassBand Flatness Performance vs. Frequency
Figure 4. SNR/SFDR Performance vs. Frequency, Sample Rate = 205 MSPS
Filter and Interface Design Procedure
In this section, a general approach to the design of the amplifier/ ADC interface with a bandpass filter is presented. To achieve optimum performance (bandwidth, SNR, and SFDR), there are certain design constraints placed on the general circuit by the amplifier and the ADC.

1. The amplifier must see the correct dc load recommended by the data sheet for optimum performance.
2. The correct amount of series resistance must be used between the amplifier and the load presented by the filter. This is to prevent undesired peaking in the pass band.
3. The input to the ADC must be reduced by external parallel resistors, and the correct series resistance must be used to isolate the ADC from the filter. This series resistor also reduces peaking.
The generalized circuit shown in Figure 5 applies to most high speed differential amplifier/ADC interfaces and was used as a basis for the bandpass filter. This design approach tends to minimize the insertion loss of the filter by taking advantage of the relatively high input impedance of most high speed ADCs and the relatively low impedance of the driving source (amplifier).
The basic design process is as follows:

1. Set the external ADC termination resistors, R_{TADC} , so that the parallel combination of R_{TADC} and R_{ADC} is between 200 Ω and 400 Ω.
2. Select R_{KB} based on experience and/or the ADC data sheet recommendations, typically between 5 Ω and 36 Ω.
3. Calculate the filter load impedance using
5. Select Z_{AAFL} so that the total load seen by the amplifier, Z_{AL}, is optimum for the particular differential amplifier chosen using the following equation:
After running these preliminary calculations, the circuit must be given a quick review for the following items.

1. The value of C_{AAF3} must be at least 10 pF so that it is several times larger than C_{ADC}. This minimizes the sensitivity of the filter to variations in C_{ADC}.
2. The ratio of Z_{AAFL} to Z_{AAFS} must not be more than about 7 so that the filter is within the limits of most filter tables and design programs.
3. The value of C_{AAF1} must be at least 5 pF to minimize sensitivity to parasitic capacitance and component variations.
4. The inductor, L_{AAF}, must be a reasonable value of at least several nH.
5. The value of C_{AFF2} and L_{AAF1} must be reasonable values. Sometimes circuit simulators can make these values too low or too high. To make these values more reasonable, simply ratio these values with better standard value components that maintain the same resonant frequency.
In some cases, the filter design program can provide more than one unique solution, especially with higher order filters. The solution that uses the most reasonable set of component values should always be chosen. Also, choose a configuration that ends in a shunt capacitor so that it can be combined with the ADC input capacitance.
Circuit Optimization Techniques and TradeOffs
The parameters in this interface circuit are very interactive; therefore, it is almost impossible to optimize the circuit for all key specifications (bandwidth, bandwidth flatness, SNR, SFDR, and gain). However, the peaking, which often occurs in the bandwidth response, can be minimized by varying R_{A} and R_{KB}.
The value of R_{A} also affects SNR performance. Larger values, while reducing the bandwidth peaking, tend to slightly increase the SNR because of the higher signal level required to drive the ADC full scale.
Select the R_{KB} series resistor on the ADC inputs to minimize distortion caused by any residual charge injection from the internal sampling capacitor within the ADC. Increasing this resistor also tends to reduce bandwidth peaking.
However, increasing R_{KB} increases signal attenuation, and the amplifier must drive a larger signal to fill the ADC input range.
For optimizing center frequency, passband characteristics, the series capacitor, C_{AAF2}, can be varied by a small amount.
Normally, the ADC input termination resistor, R_{TADC}, is selected to make the net ADC input impedance between 200 Ω and 400 Ω, which is typical of most amplifier characteristic load values. Using too high or too low a value can have an adverse effect on the linearity of the amplifier.
Balancing these tradeoffs can be somewhat difficult. In this design, each parameter was given equal weight; therefore, the values chosen are representative of the interface performance for all the design characteristics. In some designs, different values can be chosen to optimize SFDR, SNR, or input drive level, depending on system requirements.
The SFDR performance in this design is determined by two factors: the amplifier and ADC interface component values, as shown in Figure 1.
Note that the signal in this design is accoupled with the 0.1 μF capacitors to block the commonmode voltages between the amplifier, its termination resistors, and the ADC inputs. Refer to the AD9642 data sheet for further details regarding commonmode voltages.
Passive Component and PC Board Parasitic Considerations
The performance of this or any high speed circuit is highly dependent on proper printed circuit board (PCB) layout. This includes, but is not limited to, power supply bypassing, controlled impedance lines (where required), component placement, signal routing, and power and ground planes. See Tutorial MT031 and Tutorial MT101 for more detailed information regarding PCB layout for high speed ADCs and amplifiers. In addition, see the CN0227 and the CN0238.
Use low parasitic surfacemount capacitors, inductors, and resistors for the passive components in the filter. The inductors chosen are from the Coilcraft 0603CS series. The surfacemount capacitors used in the filter are 5%, C0G, 0402 type for stability and accuracy.
See the CN0279 Design Support Package for the complete documentation on the system.